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PDF KH103 Data sheet ( Hoja de datos )
| Número de pieza | KH103 | |
| Descripción | Fast Settling/ High Current Wideband Op Amp | |
| Fabricantes | Fairchild Semiconductor | |
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KH103
Fast Settling, High Current Wideband Op Amp
www.fairchildsemi.com
Features
s 80MHz full-power bandwidth (20Vpp, 100Ω)
s 200mA output current
s 0.4% settling in 10ns
s 6000V/µs slew rate
s 4ns rise and fall times (20V)
s Direct replacement for CLC103
Applications
s Coaxial line driving
s DAC current to voltage amplifier
s Flash A to D driving
s Baseband and video communications
s Radar and IF processors
Small Signal Pulse Response
Typical Performance
General Description
The KH103 is a high-power, wideband op amp designed
for the most demanding high-speed applications. The
wide bandwidth, fast settling, linear phase, and very
low harmonic distortion provide the designer with
the signal fidelity needed in applications such as driving
flash A to Ds. The 80MHz full-power bandwidth and
200mA output current of the KH103 eliminate the
need for power buffers in most applications; the
KH103 is an excellent choice for driving large high-
speed signals into coaxial lines.
In the design of the KH103 special care was taken in
order to guarantee that the output settle quickly to
within 0.4% of the final value for use with ultra fast
flash A to D converters. This is one of the most
demanding of all op amp requirements since settling
time is affected by the op amps bandwidth, passband
gain flatness, and harmonic distortion. This high
degree of performance ensures excellent performance
in many other demanding applications as well.
The dynamic performance of the KH103 is based on a
current feedback topology that provides performance
far beyond that available from conventional op amp
designs. Unlike conventional op amps where optimum
gain-bandwidth product occurs at a high gain, minimum
settling time at a gain of -1, and maximum slew rate
at a gain of +1, the KH103 provides consistent
predictable performance across its entire gain range.
For example, the table below shows how the -3dB
bandwidth remain nearly constant over a wide range
of gains. And since the amplifier is inherently stable,
no external compensation is required. The result is
shorter design time and the ability to accommodate
design changes (in gain, for example) without loss of
performance or redesign of compensation circuits.
The KH103 is constructed using thin film resistor/
bipolar transistor technology, and is available in the
following versions:
KH103AI
KH103AK
KH103AM
-25°C to +85°C 24-pin Ceramic DIP
-55°C to +125°C 24-pin Ceramic DIP,
features burn-in and
hermetic testing
-55°C to +125°C 24-pin Ceramic DIP,
environmentally screened
and electronically tested
to MIL-STD-883
REV. 1A February 2001
1 page  
KH103
DATA SHEET
with a 70kHz square wave large enough to produce a
transition from +5V to -5V at the KH103 output and
adjusting Rb until the output of U1 is at a minimum. Ra
should be about 9.5Rg for bad results; thus, Rb should be
adjusted around the value of 0.5Rg.
Figure 3: Non-Inverting Gain Composite Amplifier
to be Used with Figure 1 Circuit
Distortion and Noise
The graphs of intercept point versus frequency on the
page 3 make it easy to predict the distortion at any fre-
quency, given the output voltage of the KH103. First con-
vert the output voltage Vo to Vrms = (Vpp/2√2) and then to
P = (10log10 (20Vrms2)) to get the output power in dBm.
At the frequency of interest, its 2nd harmonic will be S2 =
(I2 - P) dB below the level of P. Its third harmonic will be
S3 = 2(I3 - P) dB below the level of P, as will the two-tone
third order intermodulation products. These approxima-
tions are useful for P < -1dB compression levels.
Approximate noise figure can determined for the KH103
using the Equivalent Input Noise graph on page 3. The
following equation can be used to determine noise figure
(F) in dB.
Figure 4: Inverting Gain Composite Amplifier to be
Used with Figure 2 Circuit
Bias Control
In normal operation, the bias control pin (pin 16) is left
unconnected. However, if control over the bias of the
amplifier is desired, the bias control pin may be driven
with a TTL signal; a TTL high level will turn the amplifier
off.
where vn is the rms noise voltage and in is the rms noise
current. Beyond the breakpoint of the curves (i.e. where
they are flat) broadband noise figure equals spot noise,
so ∆f should equal one (1) and vn and in should be read
directly off the graph. Below the breakpoint, the noise
must be integrated and ∆f set to the appropriate band-
width.
REV. 1A February 2001
5
5 Page | ||
| Páginas | Total 6 Páginas | |
| PDF Descargar | [ Datasheet KH103.PDF ] | |
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